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1 ? fn7341.1 el1527 dual channel medium power differential line driver the el1527 is a very low power dual channel differentiated amplifier designed for central office and customer premise line driving for dmt adsl solutions. this device features a high drive capability of 400ma while consuming only 7.5ma of supply current per amplifier from 12v supplies. this driver achieves a typical dist ortion of less than -75dbc, at 1mhz into a 50 ? load. the el1527 has two control pins, c 0 and c 1 , per channel. with the selection of c 0 and c 1 , the device can be set into full-i s power, 3/4-i s power, 1/2-i s power, and power-down disable modes. the el1527 maintains excellent distortion and load driving capabilities even in the lowest power settings. the el1527 is available in the thermally-enhanced 28-pin htssop package. this device is specified for operation over the full -40c to +85c temperature range. features ? drives 360ma at 16v p-p on 12v supplies ?40v p-p differential output drive into 100 ? ? -75dbc typical driver output distortion driving 50 ? at 1mhz and 1/2-i s bias current ? low quiescent current of 3.5ma per amplifier in 1/2-i s mode ? power-down disable mode applications ? adsl g.dmt and g.lite co line driving ? g.shdsl, hdsl2 line driver ? adsl cpe line driving ? video distribution amplifier ? video twisted-pair line driver pinout el1527 (28-pin htssop) top view ordering information part number package tape & reel outline # EL1527CRE 28-pin htssop - mdp0048 EL1527CRE-t7 28-pin htssop 7? mdp0048 EL1527CRE-t13 28-pin htssop 13? mdp0048 vs-(1) gnd(1) c0(1) nc c1(1) nc inb+(1) ina+(1) inb-(1) ina-(1) outb(1) outa vs+(2) nc nc vs+(1) outa(2) outb(2) ina-(2) inb-(2) ins+(2) inb+(2) nc c1(2) nc c0(2) gnd(2) vs-(2) 1 2 3 4 28 27 26 25 5 6 7 24 23 22 8 21 9 10 20 19 11 12 13 18 17 16 14 15 data sheet october 13, 2004 caution: these devices are sensitive to electrosta tic discharge; follow proper ic handling procedures. 1-888-intersil or 321-724-7143 | intersil (and design) is a registered trademark of intersil americas inc. copyright ? intersil americas inc. 2002-2004. all rights reserved. elantec is a registered trademark of elantec semiconductor, inc. all other trademarks mentioned are the property of their respective owners.
2 fn7341.1 important note: all parameters having min/max specifications are guaranteed. typ values are for information purposes only. unles s otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: t j = t c = t a absolute maxi mum ratings (t a = 25c) v s + to v s - supply voltage. . . . . . . . . . . . . . . . . . . . . . . . . . . . 26.4v v s + voltage to ground . . . . . . . . . . . . . . . . . . . . . . -0.3v to +26.4v v s - voltage to ground . . . . . . . . . . . . . . . . . . . . . . . . -26.4v to 0.3v input c 0 /c 1 to ground . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .7v v in + voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . v s - to v s + current into any input . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8ma continuous output current . . . . . . . . . . . . . . . . . . . . . . . . . . . 75ma operating temperature range . . . . . . . . . . . . . . . . .-40c to +85c storage temperature range . . . . . . . . . . . . . . . . . .-60c to +150c operating junction temperature . . . . . . . . . . . . . . .-40c to +150c power dissipation . . . . . .see po wer supplies & dissipation section caution: stresses above those listed in ?absolute maximum ratings? may cause permanent damage to the device. this is a stress o nly rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. electrical specifications v s = 12v, r f = 1.5k ? , r l = 75 ? to gnd, t a = 25c, unless otherwise specified. parameter description conditions min typ max unit ac performance bw -3db bandwidth a v = +4 70 mhz hd total harmonic distortion f = 1mhz, v o = 16v p-p , r l = 50 ? -75 dbc dg differential gain a v = +2, r l = 37.5 ? 0.17 % d differential phase a v = +2, r l = 37.5 ? 0.1 sr slewrate v out from -4.5v to +4.5v 350 500 v/s dc performance v os offset voltage -17 17 mv ? v os v os mismatch -10 10 mv r ol transimpedance v out from -4.5v to +4.5v 1 2 3.5 m ? input characteristics i b + non-inverting input bias current -5 5 a i b - inverting input bias current -30 30 a ? i b -i b - mismatch -20 20 a e n input noise voltage 2.8 nv hz i n + +input noise current 1.8 pa/ hz i n - -input noise current 19 pa/ hz v ih input high voltage c 0 & c 1 inputs 2.3 v v il input low voltage c 0 & c 1 inputs 1.5 v i ih1 input high current for c 1 c 1 = 5v 0.2 8 a i ih0 input high current for c 0 c 0 = 5v 0.1 4 a i il input low current for c 1 or c 0 c 1 = 0v, c 0 = 0v -1 1 a output characteristics v out loaded output swing single ended r l = 100 ? to gnd 10.3 10.9 v v out p loaded output swing single ended r l = 25 ? to gnd 9.5 10.2 v v out n loaded output swing single ended r l = 25 ? to gnd -9.0 -9.8 v i out output current r l = 0 ? 500 ma supply v s supply voltage single supply 5 24 v i s + (full power) positive supply current per amplifier all outputs at 0v, c 0 = c 1 = 0v 7.5 9 ma i s - (full power) negative supply current per amplifier all outputs at 0v, c 0 = c 1 = 0v -7 -8.5 ma
3 fn7341.1 typical performance curves i s + (3/4 power) positive supply current per amplifier all outputs at 0v, c 0 = 5v, c 1 = 0v 6 7.5 ma i s - (3/4 power) negative supply current per amplifier all outputs at 0v, c 0 = 5v, c 1 = 0v -5.5 -7 ma i s + (1/2 power) positive supply current per amplifier all outputs at 0v, c 0 = 0v, c 1 = 5v 3.9 5.1 ma i s - (1/2 power) negative supply current per amplifier all outputs at 0v, c 0 = 0v, c 1 = 5v -3.3 -4.6 ma i s + (power down) positive supply current per amplifier all outputs at 0v, c 0 = c 1 = 5v 0.6 1 ma i s - (power down) negative supply current per amplifier all outputs at 0v, c 0 = c 1 = 5v 0 0.75 ma i gnd gnd supply current per amplifier all outputs at 0v 0.6 1 ma electrical specifications v s = 12v, r f = 1.5k ? , r l = 75 ? to gnd, t a = 25c, unless otherwise specified. parameter description conditions min typ max unit figure 1. differential frequency response vs r f (full power mode) figure 2. differential frequency response vs r f (full power mode) figure 3. differential frequency response vs r f (3/4-power mode) figure 4. differential frequency response vs r f (3/4-power mode) 28 24 20 16 12 8 100k 1m 10m 100m frequency (hz) gain (db) v s =12v a v =10 r l =100 ? 2k 1k 1.5k 22 18 14 10 6 2 gain (db) 100k 1m 10m 100m frequency (hz) v s =12v a v =5 r l =100 ? 2k 1k 1.5k 2k 1k 1.5k 28 24 20 16 12 8 gain (db) 100k 1m 10m 100m frequency (hz) v s =12v a v =10 r l =100 ? 22 18 14 10 6 2 gain (db) 100k 1m 10m 100m frequency (hz) v s =12v a v =5 r l =100 ? 2k 1k 1.5k
4 fn7341.1 typical performance curves figure 5. differential frequency response vs r f (1/2-power mode) figure 6. differential frequency response vs r f (1/2-power mode) figure 7. differential response vs c load (full power mode) figure 8. differential response vs c load (3/4-power mode) figure 9. differential response vs c load (1/2-power mode) figure 10. differential bandwidth vs supply voltage 28 24 20 16 12 8 gain (db) 100k 1m 10m 100m frequency (hz) 2k 1k 1.5k v s =12v a v =10 r l =100 ? 22 18 14 10 6 2 gain (db) 100k 1m 10m 100m frequency (hz) v s =12v a v =5 r l =100 ? 2k 1k 1.5k 30 22 14 6 -2 -10 100k 1m 10m 100m frequency (hz) gain (db) 0pf 22pf 10pf v s =12v a v =5 r l =100 ? r f =1.5k 30 22 14 6 -2 -10 gain (db) 100k 1m 10m 100m frequency (hz) v s =12v a v =5 r l =100 ? r f =1.5k 0pf 22pf 10pf 30 22 14 6 -2 -10 gain (db) 100k 1m 10m 100m frequency (hz) v s =12v a v =5 r l =100 ? r f =1.5k 0pf 22pf 10pf 55 50 45 40 35 30 56789101112 v s (v) bandwidth (mhz) full power 3/4-power 1/2-power a v =5 r f =1.5k r l =100 ?
5 fn7341.1 typical performance curves figure 11. differential harmonic distortion vs differential output amplitude (full power mode) figure 12. supply current vs supply voltage figure 13. differential harmonic distortion vs differential output amplitude (3/4-power mode) figure 14. differential total harmonic distortion vs differential output amplitude figure 15. differential harmonic distortion vs differential output amplitude (1/2-power mode) figure 16. differential total harmonic distortion vs differential output amplitude -50 -60 -90 2 1018263442 v op-p (v) hd (db) -70 -80 -85 -55 -65 -75 v s =12v a v =5 r l =100 r f =1.5k f=1mhz hd2 hd3 18 14 10 6 2 0 024681012 v s (v) i s (ma) 16 12 8 4 i s + ( f u l l p o w e r ) i s - ( f u l l p o w e r ) i s + ( 3 / 4 p o w e r ) i s - ( 3 / 4 p o w e r ) i s + ( 1 / 2 p o w e r ) i s - ( 1 / 2 p o w e r ) -50 -60 -90 2 1018263442 v op-p (v) hd (db) -70 -80 -85 -55 -65 -75 v s =12v a v =10 r l =100 r f =1.5k f=1mhz hd3 hd2 -40 -50 -90 2 1018263442 v op-p (v) thd (db) -60 -70 -80 v s =6v v s =12v r f =1.5k a v =5 r l =100 f=150khz all power levels -50 -60 -90 2 1018263442 v op-p (v) hd (db) -70 -80 -85 -55 -65 -75 v s =12v a v =10 r l =100 r f =1.5k f=1mhz hd2 hd3 -50 -55 -60 -65 -70 -80 23442 v op-p (v) thd (db) -75 10 18 26 v s =12v a v =5 r l =100 r f =1.5k f=1mhz full power 1/2 power 3/4 power full power
6 fn7341.1 typical performance curves figure 17. differential harmonic distortion vs differential output amplitude (3/4-power mode) figure 18. differential harmonic distortion vs differential output amplitude (1/2-power mode) figure 19. differential harmonic distortion vs differential output amplitude (full power mode) figure 20. differential total harmonic distortion vs differential output amplitude figure 21. output impedance vs frequency (all power levels) figure 22. channel separation vs frequency (all power levels) -45 -60 -90 2 6 10 14 18 20 v op-p (v) hd (db) -70 -80 -85 -50 -65 -75 -55 4 8 12 16 v s =6v a v =5 r l =100 r f =1.5k f=1mhz hd3 hd2 -45 -55 -90 2 6 10 14 18 20 v op-p (v) hd (db) -70 -80 -85 -50 -60 -75 -65 4 8 12 16 v s =6v a v =5 r l =100 r f =1.5k f=1mhz hd2 hd3 -45 -55 -90 24 8 12 16 20 v op-p (v) hd (db) -65 -75 -85 -50 -60 -70 -80 6 101418 v s =6v a v =5 r l =100 r f =1.5k f=1mhz hd2 hd3 -45 -50 -80 24 8 12 16 20 v op-p (v) thd (db) -60 -70 -75 -55 -65 6 101418 v s =6v a v =5 r l =100 r f =1.5k f=1mhz full power 1/2 power 3/4 power 100 0.001 10k 100k 1m 100m frequency (hz) output impedance ( ? ) 0.1 0.01 10 1 10m v s =12v a v =1 r f =1.5k -10 10k 100k 1m 10m 100m frequency (hz) channel separation (db) -30 -50 -90 -70 -110 b a a b
7 fn7341.1 typical performance curves figure 23. psrr vs frequency figure 24. transimpedance (rol) vs frequency figure 25. voltage and current noise vs frequency figure 26. differential gain figure 27. differential phase figure 28. differential phase 20 0 -80 10k 100m frequency (hz) psrr (db) -40 -20 100k 1m -60 psrr- psrr+ 10m 10m 100 1k 100k 1m 100m frequency (hz) magnitude ( ? ) 100k 1k 1m 10k 10k 10m 40 -320 -120 -280 -40 -200 0 -160 -80 -240 phase () phase gain 100 1 10 100 10k 100k 1m 10m frequency (hz) 10 1k voltage noise (nv/ hz), current noise (pa/ hz) i b + i b - e n 0.4 0.35 0.2 0.1 0.05 0 045 number of 150 ? loads differential gain (%) 123 0.25 0.15 0.3 full power 3/4 power 1/2 power v s =12v 0.14 0.12 0 number of 150 ? loads differential phase () 0.08 0.04 0.02 0.1 0.06 v s =6v full power 1/2 power 01 345 2 3/4 power 0.12 0.1 0.06 0.02 0 01 345 number of 150 ? loads differential phase () 0.08 0.04 2 v s =12v full power 1/2 power 3/4 power
8 fn7341.1 typical performance curves figure 29. enable response figure 30. disable response figure 31. differential gain figure 32. positive supply current vs temperature figure 33. slew rate vs temperature figure 34. input bias current vs temperature ? = 48ns, m = 40ns, ch 1 = 2v, ch 2 = 2v ch 1 ch 2 c 0 , c 1 v out 40ns/div m = 400ns, ch 1 = 2v, ch 2 = 2v ch 1 ch 2 c 0 , c 1 v out 400ns/div 0.45 0 number of 150 ? loads differential gain (%) 0.25 0.05 0.35 0.15 v s =6v 045 123 0.4 0.2 0.3 0.1 full power 1/2 power 3/4 power 16 14 8 4 2 0 -50 100 150 temperature (c) supply current (ma) -25 0 50 10 6 12 125 25 75 1/2 power 3/4 power full power disabled 490 470 410 370 350 temperature (c) slew rate (v/s) 430 390 -50 100 150 -25 0 50 125 25 75 450 18 -2 temperature (c) input bias current (a) 8 0 14 4 16 6 10 2 -50 100 150 -25 0 50 125 25 75 12 ib+ ib-
9 fn7341.1 typical performance curves figure 35. output voltage vs temperature figure 36. offset voltage vs temperature figure 37. transimpedance vs temperature figure 38. package power dissipation vs ambient temperature figure 39. package power dissipation vs ambient temperature 11.8 10.8 4.8 temperature (c) output voltage (v) 8.8 6.8 5.8 9.8 7.8 -50 100 150 -25 0 50 125 25 75 r l =100 ? 10 -2 offset voltage (mv) 6 2 0 4 8 temperature (c) -50 100 150 -25 0 50 125 25 75 3.5 0 2 transimpedance (m ? ) 3 1 0.5 1.5 2.5 temperature (c) -50 100 150 -25 0 50 125 25 75 jedec jesd51-7 high effective thermal conductivity test board - htssop exposed diepad soldered to pcb per jesd51-5 4.5 4 3.5 2 1.5 0.5 0 0 25 50 75 100 150 ambient temperature (c) power dissipation (w) 4.167w j a = 3 0 c / w h t s s o p 2 8 125 85 2.5 1 3 jedec jesd51-3 low effective thermal conductivity test board 1.2 1 0.8 0.4 0.2 0 0 25 50 75 100 150 ambient temperature (c) power dissipation (w) 1.136w j a = 1 1 0 c / w h t s s o p 2 8 125 85 0.6
10 fn7341.1 applications information the el1527 consists of two se ts of high-power line driver amplifiers that can be connect ed for full duplex differential line transmission. the amplifiers are designed to be used with signals up to 4mhz and produce low distortion levels. a typical interface circuit is shown in figure 40 below. the amplifiers are wired with one in positive gain and the other in a negative gain configuration to generate a differential output for a single-ended input. they will exhibit very similar frequency respon ses for gains of three or greater and thus generate very small common-mode outputs over frequency, but for low gains the two drivers rf's need to be adjusted to give similar frequency responses. the positive-gain driver will generally exhibit more bandwidth and peaking than the negative-gain driver. if a differential signal is availa ble to the drive amplifiers, they may be wired so: each amplifier has identical positive gain connections, and optimum common-mode rejection occurs. further, dc input errors are duplicated and crea te common-mode rather than differential line errors. input connections the el1527 amplifiers are some what sensitive to source impedance. in particular, they do not like being driven by inductive sources. more than 100nh of source impedance can cause ringing or even oscillations. this inductance is equivalent to about 4? of unshielded wiring, or 6? of unterminated transmission line. normal high-frequency construction obviates any such problem. power supplies & dissipation due to the high power drive capability of the el1527, much attention needs to be paid to power dissipation. the power that needs to be dissipated in the el1527 has two main contributors. the first is the quiescent current dissipation. the second is the dissipation of the output stage. the quiescent power in the el 1527 is not constant with varying outputs. in reality, 7ma of the 15ma needed to power the drivers is converted in to output current. therefore, in the equation be low we should subtract the average output current, i o , or 7ma, whichever is the lowest. we?ll call this term i x . therefore, we can determine a quiescent current with the equation: where: ?v s is the supply voltage (v s + to v s -) ?i s is the maximum quiescent supply current (i s + + i s -) ? ix is the lesser of i o or 7ma (generally i x = 7ma) the dissipation in the output stage has two main contributors. firstly, we have the average voltage drop across the output transistor and secondly, the average output current. for minimal power dissipation, the user should select the supply voltage and the line transformer ratio accordingly. the supply voltage should be kept as low as possible, while the transformer ratio should be selected so that the peak voltage required from the el1527 is close to the maximum available output swing. there is a trade off, however, with the selection of transformer ratio. as the ratio is increased, the receive signal available to the receivers is reduced. once the user has selected the transformer ratio, the dissipation in the output st ages can be selected with the following equation: figure 40. typical line interface connection - + - + - + - + receive out - receive out + driver input r g r f r f r f r r in r r in r f r out r out line + line - receive amplifiers z line figure 41. drivers wired for differential input - + - + 2r g r f r f p dquiescent v s i s 2i x ? () = p dtransistors 2i o v s 2 ------- ? ? v o ? ? ? =
11 fn7341.1 where: ?v s is the supply voltage (v s + to v s -) ?v o is the average output voltage per channel ?i o is the average output current per channel the overall power dissipation (p diss ) is obtained by adding p dquiescent and p dtransistor . then, the ja requirement needs to be calculated. this is done using the equation: where: ?t junct is the maximum die temperature (150c) ?t amb is the maximum ambient temperature ?p diss is the dissipation calculated above ? ja is the junction to ambient thermal resistance for the package when mounted on the pcb this ja value is then used to calculate the area of copper needed on the board to dissipate the power. the cre power packages are designed so that heat may be conducted away from the device in an efficient manner. to disperse this heat, the bottom diepad is internally connected to the mounting platform of the die. heat flows through the diepad into the circuit board copper, then spreads and convects to air. thus, the ground plane on the component side of the board becomes the heatsink. this has proven to be a very effective technique. ja of 30c/w can be achieved. single supply operation the el1527 can also be powered from a single supply voltage. when operating in this mode, the gnd pins can still be connected directly to gnd. to calculate power dissipation, the equations in the previous section should be used, with v s equal to half the supply rail. output loading while the drive amplifiers ca n output in excess of 400ma transiently, the internal metallization is not designed to carry more than 75ma of steady dc current and there is no current-limit mechanism. this allows safely driving rms sinusoidal currents of 2 x 75ma , or 150ma. this current is more than that required to drive line impedances to large output levels, but output short ci rcuits cannot be tolerated. the series output resistor will usually limit currents to safe values in the event of line shorts . driving lines with no series resistor is a serious hazard. the amplifiers are sensitive to capacitive loading. more than 25pf will cause peaking of the frequency response. the same is true of badly termin ated lines connected without a series matchi ng resistor. power supplies the power supplies should be well bypassed close to the el1527. a 3.3f tantalum capacitor for each supply works well. since the load currents are differential, they should not travel through the board copper and set up ground loops that can return to amplifier inputs. due to the class ab output stage design, these currents have heavy harmonic content. if the ground terminal of the positive and negative bypass capacitors are connected to each other directly and then returned to circuit ground, no such ground loops will occur. this scheme is employed in the layout of the el1527 demonstration board, and documentation can be obtained from the factory. feedback resistor value the bandwidth and peaking of the amplifiers varies with supply voltage somewhat a nd with gain settings. the feedback resistor values can be adjusted to produce an optimal frequency response. here is a series of resistor values that produce an optimal driver frequency response (<1db peaking) for different supply voltages and gains: power control function the el1527 contains two forms of power control operation. two digital inputs, c 0 and c 1 , can be used to control the supply current of the el1527 dr ive amplifiers. as the supply current is reduced, the el1527 will start to exhibit slightly higher levels of distortion and the frequency response will be limited. the four power modes of the el1527 are set up as shown in the table below . ja t junct t amb ? () p diss ------------------------------------------------- = optimum driver feedback resistor for various gains and supply voltages supply voltage driver voltage gain 2.5 5 10 5v 2k 1.8k 1.5k 12v 2k 1.8k 1.5k power modes of the el1527 c 1 c 0 operation 00i s full power mode 0 1 3/4-i s power mode 1 0 1/2-i s power mode 1 1 power down
12 all intersil u.s. products are manufactured, asse mbled and tested utilizing iso9000 quality systems. intersil corporation?s quality certifications ca n be viewed at www.intersil.com/design/quality intersil products are sold by description only. intersil corpor ation reserves the right to make changes in circuit design, soft ware and/or specifications at any time without notice. accordingly, the reader is cautioned to verify that data sheets are current before placing orders. information furnishe d by intersil is believed to be accurate and reliable. however, no responsibility is assumed by intersil or its subsidiaries for its use; nor for any infringements of paten ts or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of intersil or its subsidiari es. for information regarding intersil corporation and its products, see www.intersil.com fn7341.1 package outline diagram

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